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\newcommand{\SC}[1]{\textsc{#1}}
\newcommand{\SCY}[0]{\SC{Yes}}
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%
\title{Normalization of Power Spectral Density estimates}
\author{Andrew J. Barbour and Robert L. Parker}
%
\begin{document}
\maketitle
%
\begin{abstract}
  A vast and deep pool of
  literature exists on the subject of spectral 
  analysis; wading through it can
  obscure even the most
  fundamental concepts
  from the inexperienced practitioner.
  Appropriate interpretation of spectral analyses
  depends crucially on the normalization used, 
  which is often the greatest source of confusion.
  Here we outline
  the normalization used by \psd{}, namely
  the \bidx{single-sided}
  \bidx{power spectral density} (PSD).
  We briefly outline the background mathematics,
  present an example from scratch,
  and compare the results with
  the normalization used by 
  the spectrum estimator included in the base distribution of
  R: \Rcmd{stats::spectrum}.
\end{abstract}

\tableofcontents

%%
%%
%%
\section{Introduction}

There can often be confusion about the different quantities used
in spectral analysis,
partly due to myriad nomenclature within the incredibly vast literature
on the subject\footnote{
The type of
confusion common in spectral analyses
is illustrated in this thread on \Rcmd{R-help}:
\url{https://r.789695.n4.nabble.com/Re-How-do-I-normalize-a-PSD-td792902.html}
}.
Commonly one finds similarly sounding phrases, including ``amplitude spectrum",
``energy spectral density", ``power", ``power spectra", and even ``spectra".
These all mean \emph{something}, but are rarely equivalent, and are
sometimes used improperly.
To clarify these terms, we will tread somewhat lightly through the background and
definitions used in spectral analysis, 
without overly complicating the discussion with proofs.

\section{Power spectral density}

We begin by considering a 
stationary stochastic process \dXstoch{}, a random function extending 
throughout all time with time-invariant properties. 
Our goal is to characterize \dXstoch{} with an 
ordinary function describing
its properties in frequency 
(as the autocorrelation function does in time).

Functions
of a real variable (continuous
time signals)
will have a Fourier transform
\begin{equation}
\label{eq-FT-0}
\stochXfo (f) = \Fo \{ \dXstoch{} \} = 
\intone \dXstoch{} e^{-2 \pi i f t} \, dt
\end{equation}
%
and for discrete-time signals \dXstochd{} the spectrum is restricted
to the finite interval
\begin{equation}
\label{eq-DFT-0}
\stochXfo (f) =  \sum_{n=-\infty}^{\infty} \dXstochd{} e^{-2 \pi i f n}, -1/2 \leq f \leq 1/2
\end{equation}
which means we can reconstruct the original
series from the inverse transform of (\ref{eq-DFT-0}), 
over frequencies $(\nhalf,\,\half)$:
\begin{equation}
\label{eq-FT-0d}
\dXstochd{} = \Fo^{-1} \{ \stochXfo (f) \} = 
\int_{\nhalf}^{\half} \dXstoch{} e^{2 \pi i f n} \, df
\end{equation}

There is a problem with the definitions we have just presented.
The integral in (\ref{eq-FT-0}) or the 
sum in (\ref{eq-DFT-0}) must converge to apply these equations to
their corresponding stochastic processes; this would
require some kind 
of decrease in amplitude, or energy, as $t$ or $n$ gets large which
does not happen for a stationary process.
And, if we put a stochastic process in $f(t)$ in (\ref{eq-FT-0})
we would obtain another random function, which is contrary to our stated
goal of obtaining a descriptive function in frequency space.

\subsection{An informal definition from a digital filtering analogy}

Suppose we wanted to know 
how much variability the stationary process exhibits at a 
frequency $f_0$. We could design a narrow bandpass 
filter $\phi_f$ that only allowed signals through in the frequency 
band $( f_0 - \half \Delta f , f_0 + \half \Delta f )$ with unit gain. 
If we convolve a signal $X$ with that filter to obtain
the process $X_\phi$, we will have a
stochastic process having very limited frequency content.
We would expect the variance (a measure of amplitude)
to be proportional to the width $\Delta f$ of the bandpass filter, which
prevents the condition of infinite energy at infinite time (or length).
The variance of the filtered process $X_\phi$ will be some
positive value times $\Delta f$, and will vary as the center 
frequency $f_0$ is varied.
At the frequency $f_0$ the following is also true:
$$
\Var \{X_\phi\} \propto \Var\{X\}
$$
The variance of $X$ in
a frequency band is called the \bidx{power} in that band, and 
so $S_X$ is the power spectrum of $X$, or more grandly its
\bidx{power spectral density}:

\begin{equation}
\label{eq-PSD-informal}
S_X ( f_0 ) \Delta f = \Var \{\phi_f \star X\}
\end{equation}

Equation (\ref{eq-PSD-informal}) is our informal definition of $S_X ( f_0 )$. 
Notice this definition works equally well for continuous
or discrete processes. 
In the days before computers, 
analog spectral analyzers were built based on this 
principle: a large number of narrow bandpass filters
followed by rectifiers to measure the variance in each band.

We can demonstrate this analogy by plotting the 
PSDs obtained for a normally distributed process, and
a bandpass filtered version of it, along with
the filter's amplitude response.
In Figure \ref{fig:filter} we see that
within the pass-band the variance
of the filtered process
is equal to that of the infinitely long process.
We could imagine the grey curve being comprised of a 
collection of passband responses.
If we could construct a true bandpass filter, there would be 
zero energy outside the passband; but, in practice 
the filter weights create side-lobe 
energy which is unavoidable.
Also note the artificial bias
from spectral leakage, seen just outside the 
edges of the pass-band.
%and near the zero frequency.
%
<<eval=TRUE, echo=TRUE, label="Filteredsignalanalogy">>=
set.seed(1234)
N <- 1028
x <- rnorm(N, mean = 0, sd = 1)
# Load signal processing
library(signal, warn.conflicts=FALSE)
# Construct an FIR filter
f <- c(0, 0.2, 0.2, 0.3, 0.3, 0.5)*2
m <- c(0, 0, 1, 1, 0, 0)
fw <- signal::fir2(N, f, m)
# complex filter response
fh <- signal::freqz(fw, Fs=1)
f <- c(0, 0.12, 0.12, 0.22, 0.22, 0.5)*2
fwl <- signal::fir2(N, f, m)
fhl <- signal::freqz(fwl, Fs=1)
f <- c(0, 0.28, 0.28, 0.38, 0.38, 0.5)*2
fwu <- signal::fir2(N, f, m)
fhu <- signal::freqz(fwu, Fs=1)
# convolution
xf <- signal::filter(fw, x)
# PSD using stats::spectrum
Sx <- spectrum(x, pad=1, plot=FALSE, taper=0.2)
Sxf <- spectrum(xf, pad=1, plot=FALSE, taper=0.2)
@
%
\begin{figure}[htb!]
\begin{center}
<<eval=TRUE, echo=FALSE, fig.width=6, fig.height=3, label=FILTERS>>=
Sx$df <- Sx$bandwidth <- NA
par(mar=c(0,0,2,0), oma=rep(0,4))
plot(Sx, col="grey", log="dB", ylim=c(-150,20), xlim=c(0.1,0.4),
xlab="", ylab="", ci.col=NA, axes=FALSE,
main="PSDs of raw and filtered process")
lines(fhu$f, 20*log10(Mod(fhu$h)), col="red", lty=3, lwd=2)
lines(fhl$f, 20*log10(Mod(fhl$h)), col="red", lty=3, lwd=2)
lines(fh$f, 20*log10(Mod(fh$h)), col="red", lwd=2)
plot(Sxf, log="dB", add=TRUE)
@
\caption{Demonstration of the ``filter analogy". 
A normally-distributed
process (with PSD in grey) is convolved with a bandpass
filter (with a response shown in red); the resulting PSD is in black.
In this analogy the PSD is the variance of a stationary 
process in an infinitesimally narrow band, as if we had 
passed our signal through a bank of narrow filters (dotted lines)
and looked at the output from each one.
}
\label{fig:filter}
\end{center}
\end{figure}
%fftshift<-function(X){
% Mi <- length(X)
% Pi <- ceiling(Mi/2)
% indices <- c(((Pi+1):Mi),seq_len(Pi))
% return(X[indices])
%}

\subsection{A more formal definition}
Let us return to having a single realization
of a stochastic process in the time domain, 
\dXstoch{}, which we assume is sampled over a finite interval of time
$(-T/2, \,T/2)$, and denoted by \dXrealiz{}.
A realization of \dXstoch{} will have
a Fourier transform:
%
\begin{equation}
\label{eq-FT}
\Xfo_T (f) = \Fo \{ \dXrealiz{} \} = 
\intone \dXrealiz{} e^{-2 \pi i ft} \, dt = 
\int_{-T/2}^{T/2}  \dXstoch{} e^{-2 \pi i ft} \, dt
\end{equation}
%
The \bidx{amplitude spectrum} is the modulus
of $\Xfo_T$ and the
\bidx{phase spectrum} is the argument 
of $\Xfo_T$, although these are generally not informative
for physical applications, if ever.
The \bidx{energy spectral density} is found from
$\Xfo_T$ by finding the expectation of the
squared amplitude spectrum:
%
\begin{equation}
\label{eq-ESD}
\dESD{} = \Ex \{ | \Xfo_T (f) | ^ 2 \}
\end{equation}
%
 
We note the necessity for convergence mentioned previously: 
as $T$ grows to infinity, 
so too does \dESD{}.
We divide it by the interval length $T$ to curb this growth,
which gives us an expression for
\bidx{power spectral density}:
%
\begin{equation}
\label{eq-psddef1}
\begin{split}
\dS{} & = \lim_{T \to \infty} T^{-1} \dESD{} \\
& = \lim_{T \to \infty} \Ex \left\{ \frac{1}{T} \left | 
\int_{-T/2}^{T/2}  \dXstoch{} e^{-2 \pi i ft} \, dt \right | ^ 2 \right\}
\end{split}
\end{equation}
%\label{sy-psd}
%
which is real, non-negative, and exists for all
stationary processes 
with zero mean and finite variance.

Equation (\ref{eq-psddef1}) defines
the \bidx{double-sided} PSD,
because in the limit of $T$, the limits of integration are $\pm\infty$.
If \dXstoch{} is real the power spectrum \dS{} is even; hence,
we only need estimates for $f \ge 0$.
The \bidx{single-sided} PSD is thus given by $2 S(f)$ for $f \ge 0$.
In many cases this sidedness distinction, as we will see, explains
errant factors of two in PSD normalizations.

\subsection{Connection to the autocovariance function}
What is the connection between the PSD, defined in Equation (\ref{eq-psddef1}),
and the autocovariance function \dACV{\tau}?

From Equation (\ref{eq-psddef1}) we see that \dS{}
is obtained from products of \dXstoch{} with itself at any particular $f$,
so it is related to the second-order moment of \dXstoch{} only.
The \bidx{autocovariance} (ACV) \dACV{\tau} is also related to
the second-order moment:
%
\begin{equation}
\begin{split}
\dACV{\tau} &= \Cov \left( \dXlag{}, \dXlag{} \right) \\
         &= \Ex \left\{ \left( \dXlag{} - \Ex \{ \dXlag{} \} \right)^2 \right\}
\end{split}
\label{eq-acvdef}
\end{equation}
%
It may be surprising to note, as well, that \dS{} is
simply the Fourier transform of \dACV{\tau}:
%
\begin{equation}
\label{eq-psddef2}
\dS{} = \Fo \{ \dACV{\tau} \} =
\intone \dACV{\tau} e ^ {-2 \pi i f \tau} \, d\tau
\end{equation}
%
So, the
functions \dACV{\tau} and \dS{}
exist as a transform pair.
For real data, \dACV{\tau} is always even, and always real.
This implies that \dS{} is also a real and even function in $f$,
which, because $S(f) >= 0$, restricts the functions \dACV{t}
could possibly represent.
Put another way, there are many examples of even-functions
having non-positive Fourier transforms (\citet{bracewell2000} shows
many).

\subsection{Testing normalization}
We can use the relationship with the ACV in (\ref{eq-psddef2}), or
the informal definition in (\ref{eq-PSD-informal}),
to test whether or not a PSD is properly normalized.  
To see this, we take the
inverse Fourier transform of (\ref{eq-psddef2}):
%
\begin{equation}
\label{eq-psdinv}
\dACV{t} = \intone \dS{} e ^ {2 \pi i ft} \, df
\end{equation}
%
and find the ACV of a zero-mean 
process for zero lag.  From (\ref{eq-acvdef}) we have:
%
\begin{equation}
\label{eq-acvprop}
\dACV{0} = \Ex \{ \dXstoch{}^2 \} = \Var \{ \dXstoch{} \} = \sigma_\mathcal{X} ^ 2
\end{equation}
%
and by setting $t = 0$ in
(\ref{eq-psdinv}) we have the basis of our normalization test:
%
\begin{equation}
\label{eq-psdnorm}
\sigma_\mathcal{X} ^ 2 = \intone S (f) \, df
\end{equation}
%
That is,
the area under the power spectrum is the variance
of the process.
So, a straightforward way to test normalization 
is to compute the PSD for a realization of \dXstoch{} with
known variance, and zero mean [e.g. $\mathcal{N}(0,\sigma^2)$]; and then
calculate the integrated spectrum.
For example, the \idx{single-sided}
PSD for a realization of a $\mathcal{N}(0, 1)$ process, 
sampled at 1 Hz, 
will be flat at 2 units$^2$ Hz$^{-1}$
across the frequency band $[0, \half]$,
and will have
an area equal to one.

\subsection{Summary of nomenclature}

In Table \ref{tbl:norm} we give a summary of some
of the quantities we have reviewed.

\input{supp_norms}

%%
%%
%%
\section{A from-scratch example: White noise.}
Without using the tools in \psd{} we will build up an example
using R commands, in order to highlight the topic of normalization.

First, generate a normally distributed series\footnote{
Although a white noise process is not strictly bandlimited,
we will use it to demonstrate differences in normalization.
}, 
and then find its Discrete Fourier Transform 
(DFT)\footnote{
A proper DFT is normalized by the length of the series; however, most
DFT calculators (including \Rcmd{stats::fft}) eschew this normalization for 
efficiency's sake.
}.
<<eval=TRUE, echo=TRUE, label="SyntheticwhitenoiseandaDFT">>=
# using x from the filter analogy section
xv <- var(x)
X <- fft(x)
class(X)
length(X)
@

We can easily find the amplitude and phase response
followed by equivalent \idx{energy spectral density}
estimates\footnote{
Note the equivalence
between the complex conjugate based estimates.
}:
<<eval=TRUE, echo=TRUE, label="Amplitudeandphasespectra">>=
Sa <- Mod(X) # Amplitude spectrum
Sp <- Arg(X) # Phase spectrum
XC <- Conj(X)
Se <- Sa**2
Se_2 <- Mod(XC * X)
all.equal(Se, Se_2)
Se_2R <- Mod(X * XC)
all.equal(Se, Se_2R)
@

The single-sided \idx{power spectral density} estimates
follow once we have the Nyquist frequency,
defined as half the sampling rate:
<<eval=TRUE, echo=TRUE, label="Nyquistfrequencies">>=
fsamp <- 1  # sampling freq, e.g. Hz
fNyq <- fsamp/2   # Nyquist freq
Nf <- N/2  # number of freqs
nyfreqs <- seq.int(from=0, to=fNyq, length.out=Nf)
S <- Se[2:(Nf+1)] * 2 / N   # Finally, the PSD!
@

To approximate the integrated spectrum in the case of a ``flat" spectrum, we need
an accurate measure of the first moment of the spectral values.  
The \Rcmd{median} estimator
produces a biased estimate because the distribution
of spectral values roughly follows a $\chi^2_\nu$ distribution, where
$\nu$ is the number of degrees of freedom and, for this distribution,
the expectation of the first moment.  To find this value
we perform a
conjugate gradient based minimization of
the best-fitting $\chi^2$ distribution, and compare this
with the value returned by \Rcmd{mean}.  Our starting point will be the 
estimated mean value.  We visualize the fit with
a ``Q-Q" plot, which shows PSD quantiles values as a function of $\chi^2$ quantiles,
using the optimized value of the number of degrees of freedom; this
is shown in Figure \ref{fig:qqchi}.

<<eval=TRUE, echo=TRUE, label=OPTIMEXPECT>>=
# 0) Setup optimization function for dof, using conjugate gradients\\
#    min L1 |PSD - Chi^2(dof)|
Chifit <- function(PSD){optim(list(df=mean(PSD)), function(dof){
  sum(log(PSD)) - sum(log(dchisq(PSD, dof))) }, method="CG")}
# 1) run optimization
Schi <- Chifit(S)
# Get 'df', the degrees of freedom
print(dof <- Schi$par[[1]]) 
@
While the optimal degrees of freedom is very nearly the correct value of two (2), 
the value produced by \Rcmd{mean} is different by merely one percent (this is
certainly an acceptable bias for our purposes).
<<eval=TRUE, echo=TRUE, label=MEANEXPECT>>=
# compare with the mean and median
c(mSn <- mean(S), median(S))
@

\begin{figure}[htb!]
\begin{center}
<<eval=TRUE, echo=FALSE, fig.width=5, fig.height=5, label=QQFIT>>=
par(pty="s", las=1)
ttl <- expression("Q-Q plot for PSD and" ~~ chi^2 ~~ "fit")
qqplot(log(qchisq(ppoints(N), df=dof)), log(S), main = ttl, ylab="Spectrum quantiles", xlab="Distribution quantiles")
abline(0,1, col="red")
@
\caption{``Q-Q" plot of 
quantiles of our example PSD
 against
 theoretical $\chi^2_\nu$ quantiles.  The distribution is calculated
with a value for degrees of freedom ($\nu$) obtained from the
$L_1$-norm minimization procedure.  Such a minimization is not
generally required, since we have shown the estimator found with \Rcmd{mean}
is reasonably accurate.}
\label{fig:qqchi}
\end{center}
\end{figure}

\begin{figure}[htb!]
\begin{center}
<<eval=TRUE, echo=FALSE, fig.width=6, fig.height=3.5, label=PSD>>=
par(las=1, mgp = c(2.2, 1, 0))
ylab <- expression("units"^2 ~~ "/ frequency")
plot(nyfreqs, S, type="h", xlab="Nyquist frequency", ylab=ylab, yaxs="i")
abline(h=dof, lwd=2, col="red")
@
\caption{Power spectral density estimates for a single realization of a 
$\mathcal{N}(0,1)$ process, in linear units.  
The horizontal line shows the expectation of the spectral estimates, obtained
from the $\chi^2$ fit in Figure \ref{fig:qqchi}; this value is
used to test normalization.}
\label{fig:psdN}
\end{center}
\end{figure}

An estimate of the integrated spectrum
should roughly equal the known variance.
Figure \ref{fig:psdN} plots the PSD of our white noise series with
the value of $\nu$ from the optimization, 
with which we can perform a variance--normalization
test:
<<eval=TRUE, echo=TRUE, label="Testnormalization">>=
mSn <- dof
test_norm <- function(sval, nyq, xvar){svar <- sval * nyq; return(svar/xvar)}
print(xv_1 <- test_norm(mSn, fNyq, xv))
xv_2 <- sum(S)/Nf * fNyq / xv  # an alternate test
all.equal(xv_1, xv_2)
@

But what if the sampling frequency \texttt{fsamp} changes? An obvious change will be
the actual Nyquist frequency, which means the variance-normalization test will
fail if the PSD estimates are not re-scaled.  We simply re-scale the frequencies
and PSD
with the sampling rate
to obtain the properly-normalized spectra.

<<eval=TRUE, echo=TRUE, label="Applycorrectnormalization">>=
fsamp <- 20
fNyq <- fsamp / 2
freqs <- fsamp * nyfreqs 
Snew <- S / fsamp
# Test variance crudely
mSn <- mean(Snew)
test_norm(mSn, fNyq, xv)
@

In Figure \ref{fig:psdsamp} we
plot the PSD with new normalization, and compare it to
the previous normalization.
Spectral values are shown as
decibels (relative to 1 units$^2$ Hz$^{-1}$), using:

<<eval=TRUE, echo=TRUE, label="DB">>=
# decibel function
dB <- function(y) 10*log10(y)
@
\begin{figure}[htb!]
\begin{center}
<<eval=TRUE, echo=FALSE, fig.width=6, fig.height=3.8, label=PSD2>>=
par(las=1)
plot(freqs, dB(S), type="l", col="dark grey", xlab="Frequency", ylab="dB")
lines(freqs, dB(Snew), lwd=1.3)
lines(c(0,fNyq), rep(dB(mSn),2), lwd=3, col="red")
abline(h=dB(1/fNyq), col="blue")
@
\caption{Rescaled PSD estimates for a single realization of a 
$\mathcal{N}(0,1)$ process with a sampling rate of 20 s$^{-1}$ rather
than 1 s$^{-1}$ as from before.  
The original spectrum (grey) is scaled to the appropriate level
(black).
The thick red line shows the mean (rescaled) spectral level, and the
blue line shows the predicted mean value based on twice the sampling
frequency.}
\label{fig:psdsamp}
\end{center}
\end{figure}

\section{Normalization used in \Rcmd{stats::spectrum}}

The PSD estimator included in
the core distribution of R is \Rcmd{stats::spectrum}, which
calls either \Rcmd{stats::spec.ar} or \Rcmd{stats::spec.pgram} for 
cases of
parametric and non-parametric estimation, respectively.  
For this discussion we compare to \Rcmd{spec.pgram};
the user can optionally apply a single cosine taper, 
and/or a smoothing kernel.

By default \Rcmd{spec.pgram} assumes the sampling frequency
for the input series is 1, and normalizes accordingly; however,
the sampling information may be specified by creating a \Rcmd{ts}
object from the series prior to spectrum estimation:

<<eval=TRUE, echo=TRUE, label="Changethesamplingfrequency">>=
fsamp <- 20
xt <- ts(x, frequency=fsamp)
pgram20 <- spec.pgram(xt, pad=1, taper=0, plot=FALSE)
pgram01 <- spec.pgram(ts(xt, frequency=1), pad=1, taper=0, plot=FALSE)
@

We plot the two PSD estimates on the same scales, in Figure \ref{fig:rawpgram}, utilizing
the plot method for \Rcmd{spec} objects: \Rcmd{plot.spec}.
We also show horizontal lines corresponding to the inverse of twice
the sampling rate, which puts the spectra about a factor of 2 too low:
<<eval=TRUE, echo=TRUE>>=
mSn/mean(pgram20$spec)
@

\begin{figure}[htb!]
\begin{center}
<<eval=TRUE, echo=FALSE, fig.width=6, fig.height=3.5, label=NORMS>>=
par(las=1)
plot(pgram01, log="dB", xlim=c(0,10), ylim=36*c(-1,.3), main="", col="dark grey")
plot(pgram20, log="dB", add=TRUE)
abline(h=-dB(c(1, 20)*2), col=c("dark grey","black"))
abline(v=.5*c(1,20), lty=3)
#lines(c(0,fNyq), rep(dB(mSn),2), lwd=1.5, col="red")
abline(h=dB(1/fNyq), col="blue")
@

\caption{Power spectral densities from \Rcmd{spec.pgram} for the same
data series.  The grey series is the PSD for a sampling rate of 1; whereas,
the black series is the PSD for a sampling rate of 20.
The horizontal lines show levels corresponding to the inverse of
twice the sampling rate (black and grey), and 
the expected spectral level for the 20 Hz sampling (blue).
Vertical lines show the respective Nyquist frequencies.}
\label{fig:rawpgram}
\end{center}
\end{figure}

Because the frequencies are clearly correct, this factor of two likely means
the spectra will fail our
simple variance-normalization test. They do fail, by a factor of two,
again too low:
<<eval=TRUE, echo=TRUE, label="Testthenormalizationagain">>=
test_norm(mean(pgram01$spec), 0.5, xv)
test_norm(mean(pgram20$spec), 10, xv)
@

But why?  This errant factor of two comes from
the assumption of a
\idx{double-sided} spectrum, which 
is at odds with our definition of the 
\idx{single-sided} spectrum
by (you guessed it) a factor of two.
We can illustrate this with the following example, where
we compare the PSDs from \Rcmd{spec.pgram} for a real
and complex series:

<<eval=TRUE, echo=TRUE, label="DoublesidedPSDfromspectrum">>=
psd1 <- spec.pgram(x, plot=FALSE)
psd2 <- spec.pgram(xc<-complex(real=x, imag=x), plot=FALSE, demean=TRUE)
mx <- mean(Mod(x))
mxc <- mean(Mod(xc))
(mxc/mx)**2
mean(psd2$spec / psd1$spec)
@

Again, a factor of two. 
This means that unless we are interested in analyzing complex
timeseries, we need only multiply by two 
to obtain properly normalized spectra
from \Rcmd{spectrum}, 
assuming the sampling information is included in the series.

\section{PSD estimators in R}
The suite of extensions having
similar functionality to \psd{}
is relatively limited; however, there are at least four which
can produce sophisticated PSD estimates.   We have
summarized the available functions in Table \ref{tbl:methods}
so far as we know.
%\footnote{
%As of this writing (Jun 2020), \Rcmd{sapa} has been removed from CRAN.
%}.

\input{supp_specprogs}

\section{Acknowlegements}
We thank Richard Gaal for catching a subtle error in the from-scratch example.

%\pagebreak
\section*{Session Info}
<<eval=TRUE, echo=TRUE, label=SI>>=
utils::sessionInfo()
@

%% bib and index

%\pagebreak
\bibliographystyle{apalike}
\bibliography{REFS}

\end{document}
